Battery charger with protection circuitry

ABSTRACT

The charger includes a controller, a battery power source having at least two power settings connected to the controller, a power supply connectable to an outside power source, the power supply receiving a current and voltage from the outside power source for providing power to at least one of the controller and the battery power source, and a foldback circuit for switching between two power settings depending upon at least one of the current and voltage received from the outside power source.

The following application derives priority from U.S. Application No. 60/369,769, filed Apr. 3, 2002, now pending, and U.S. Application No. 60/377,184, filed on May 1, 2002, now pending.

FIELD OF THE INVENTION

This invention relates generally to battery chargers and more particularly to battery chargers with protection circuitry.

BACKGROUND OF THE INVENTION

The battery packs for portable power tools, outdoor tools and certain kitchen and domestic appliances may include rechargeable batteries, such as lithium, nickel cadmium, nickel metal hydride and lead-acid batteries, so that they can be recharged rather than be replaced. Thereby a substantial cost saving is achieved.

Some chargers can be connected to a vehicle battery, such as a car battery. Referring to FIG. 1, car battery 1 can-be connected to charger 20 via a lighter plug 5. Charger 20 in turn charges battery pack 10.

Two virtual resistors 3, 4 may exist between car battery 1 and charger 20. Virtual resistors 3, 4 represent the inherent resistance before and after the lighter plug connection, which in turn create voltage drops. Accordingly, the voltage V_(IN) received by the charger 20 may not necessarily be equal to the voltage of car battery 1.

A fuse 2 may also be provided between car battery 1 and charger 20. Typically, such fuse 2 has a rating of about 8 amps. In other words, if the current I_(IN) going to charger 20 is larger than about 8 amps, the fuse 2 will open.

This could be problematic as charger 20 typically sends an effective constant current I_(OUT) to battery pack 10. Such problem arises because of the following equation: (V _(IN))(I _(IN))k=(V _(PACK))(I _(OUT)),

where V_(IN), I_(IN), and I_(OUT) are defined above,

k is the charger efficiency constant, and

V_(PACK) is the voltage of battery pack 10.

Under such equation, since V_(PACK) is set by the battery pack, and I_(OUT) as set by the charger and the charger efficiency constant k are relatively constant, the only two variables remaining are V_(IN) and I_(IN). If V_(IN) drops below a certain threshold, I_(IN) will have to increase to maintain the equation. However, if I_(IN) increases beyond a certain threshold, it will force fuse 2 to open, thus prematurely ending charging.

SUMMARY OF THE INVENTION

In accordance with the present invention, an improved battery pack charger is employed. The charger includes a controller, a battery power source having at least two power settings connected to the controller, at least one terminal connected to at least one of the controller and the battery power source, a power supply connectable to an outside power source, the power supply receiving a current and voltage from the outside power source for providing power to at least one of the controller and the battery power source, and a foldback circuit for switching between two power settings depending upon at least one of the current and voltage received from the outside power source.

Additional features and benefits of the present invention are described, and will be apparent from, the accompanying drawings and the detailed description below.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings illustrate preferred embodiments of the invention according to the practical application of the principles thereof, and in which:

FIG. 1 is a simplified block diagram of a battery pack and charger;

FIG. 2 illustrates an exemplary charger according to the present invention, where FIG. 2A is a block diagram of a battery pack and the charger, and FIG. 2B is a schematic diagram of the charger;

FIG. 3 is a flowchart showing a method according to the present invention;

FIG. 4 is a simplified block diagram of an alternate battery pack and charger;

FIG. 5 is a schematic diagram of the watchdog circuit according to the invention;

FIG. 6 is a schematic diagram of the charger including the watchdog circuit of FIG. 5;

FIG. 7 is a simplified block diagram of another alternate charmer; and

FIG. 8 is a schematic diagram of an alternate watchdog circuit according to the invention.

DETAILED DESCRIPTION

The invention is now described with reference to the accompanying figures, wherein like numerals designate like parts.

Referring to FIGS. 1-2, a battery pack 10 is connected to a charger 20. Battery pack 10 may comprise a plurality of battery cells 11 connected in series and/or parallel, which dictate the voltage and storage capacity for battery pack 10. Battery pack 10 may include three battery contacts: first battery contact 12, second battery contact 13, third battery contact 14 and fourth battery contact 16. Battery contact 12 is the B+ (positive) terminal for battery pack 10. Battery contact 14 is the B− or negative/common terminal. Battery contact 13 is the S or sensing terminal. Battery contacts 12 and 14 receive the charging current sent from the charger 20 (preferably from current source 22, as discussed below) for charging the battery pack 10.

As shown in FIG. 2, the battery cells 11 are connected between the battery contacts 12 and 14. In addition, preferably connected between battery contacts 13 and 14 is a temperature sensing device 15, such as a negative temperature co-efficient (NTC) resistor, or thermistor, R_(T). The temperature sensing device is preferably in closer proximity to the cells 11 for monitoring of the battery temperature. Persons skilled in the art will recognize that other components, such as capacitors, etc., or circuits can be used to provide a signal representative of the battery temperature.

Battery pack 10 may also comprise an identifier as known in the prior art, such as resistor R_(ID), so that charger 20 can identify the type and capacity of the battery pack, and charge accordingly. Resistor R_(ID) is preferably connected between battery contacts 16 and 14, where battery contact 16 is the ID terminal.

The charger 20 preferably comprises a controller 21, which in turn includes positive terminal (B+) 17 and negative (B−) terminal 18, which are coupled to battery pack 10 via battery contacts 12 and 14, respectively. The positive terminal may also act as an input, preferably an analog/digital input, in order for the controller 21 to detect the battery pack voltage. In addition, the controller 21 may include another input TC, preferably an analog/digital input, which is coupled to the temperature sensing device 15 via the third battery contact 13 (S). This allows the controller 21 to monitor the battery temperature.

Controller 21 may include a microprocessor 23 for controlling the charging and monitoring operations. Controller 21 may control a charging power source for providing power to the battery pack 10, such as current source 22 that provides current to battery pack 10. This current may be a fast charging current and/or an equalization current. Current source 22 may be integrated within controller 21.

Controller 21 may have a memory 25 for storing data. Memory 25 may be integrated within controller 21 and/or microprocessor 23.

The charger 20, and its elements within, including controller 21, microprocessor 23, and current source 22, receive the necessary power from a DC mains power supply 24, which may be ultimately connected to car battery 1. DC mains power supply 24 may convert the power received from the vehicle battery to the necessary power requirements of the different elements, as is well known in the art. DC mains power supply 24 may include a filter, which in turn may include capacitors C1, C2, C3, C36, and C34 and inductors L1, L2, L3 to filter out unwanted fluctuations in the input voltage.

Controller 21 may also control a fan 25. Fan 25 preferably blows air towards the battery pack 10 for cooling the battery pack 10.

In order to avoid opening fuse 2 because of a high I_(IN), it is preferable to provide a foldback circuit 26 that monitors several inputs, and lowers the current output I_(OUT) of current source 22. Foldback circuit 26 may monitor the current output I_(OUT), as well as the battery pack voltage V_(PACK). In addition, foldback circuit 26 may receive information from controller 26 and/or DC mains power supply 24 concerning input voltage V_(IN). If foldback circuit 26 determines that, based on those inputs, the input current I_(IN) will exceed a certain threshold, such as 8 amps, foldback circuit 26 will send a signal to current source 22, lowering current output I_(OUT). By lowering current output I_(OUT), input current I_(IN) is also lowered, thus preventing opening fuse 2.

Referring to FIG. 2B, foldback circuit 26 preferably works in the following manner. The connection from output B+ to diode D38 is preferably used to detect a voltage level set by diodes D38 and/or D16. When this voltage level is exceeded, transistor Q3 is preferably switched on. Transistor Q3, when in the on state, preferably ensures that transistor Q4 is in the off state by pulling the gate down to the source. Transistor Q4 is preferably used a switch to change the gain of the current sense amplifier U3:A.

Persons skilled in the art will note that pin P21 of microprocessor 23 will sense the state of the amplifier U3:A by measuring the voltage. Microprocessor 23 can also detect the output voltage V_(OUT) via pin P13 and the input voltage V_(IN) can be detected via pin P4.

Pin P21 of microprocessor 23 is preferably normally left in a high impedance state and preferably used as an input to detect the function of transistor Q3. When the microprocessor 23 needs to force the output current I_(OUT) low, it will preferably make pin P21 an output and put it in the low state, thus removing the gate drive from transistor Q4 and changing the gain of the current feedback amp U3:A. Such circuit is advantageous as it minimizes the number of components, as well as controls any unwanted oscillations.

Persons skilled in the art will recognize that foldback circuit 26 can be implemented with a circuit, as shown in FIG. 2B, or via a software algorithm, as shown in FIG. 3. Persons skilled in the art will recognize that the order of the steps discussed below may be altered.

The charging process begins upon insertion of battery pack 10 into charger 20 by the user (ST1). The charger 20 then begins charging (ST2) by sending a charge current sent from current source 22 to battery pack 10. Preferably, the fast charge current is about 2 Amps.

The controller 21 and/or microprocessor 23 reads input voltage V_(IN) (ST3). The controller 21 and/or microprocessor 23 then preferably checks whether input voltage V_(IN) is greater than a first threshold X (ST4). Preferably, first threshold X represents a high vehicle battery voltage, which may be about 17 volts for a vehicle battery rated for 12 volts.

If input voltage V_(IN) is not greater than a first threshold X, then controller 21 and/or microprocessor 23 then preferably checks whether input voltage V_(IN) is smaller than a second threshold Y (ST5). Preferably, second threshold Y represents a low vehicle battery voltage, which may be about 10 volts for a vehicle battery rated for 12 volts.

If (a) input voltage V_(IN) is not greater than a first threshold X and (b) input voltage V_(IN) is not smaller than a second threshold Y, charging of battery pack 10 continues until the charging process is terminated by removal of the battery pack 10, or by a termination algorithm, etc. The controller 21 and/or microprocessor 23 nevertheless keep reading input voltage V_(IN) and comparing input voltage V_(IN) to first and second thresholds X,Y until termination.

If (a) input voltage V_(IN) is greater than a first threshold X or (b) input voltage V_(IN) is smaller than a second threshold Y, an error subroutine may begin. It is preferable to set a counter to a certain predetermined number (ST6), such as thirty. In addition, it is preferable to turn off current source 22 (and thus the output current I_(OUT)) (ST7). A error signal may also be displayed via an LCD display or LEDs. A sound source, such as a piezoelectric element, a beeper, etc., may also be used to alert the user to the error condition.

The controller 21 and/or microprocessor 23 may again read input voltage V_(IN) (ST8). The controller 21 and/or microprocessor 23 then preferably checks whether input voltage V_(IN) is greater than a third threshold A (ST9). Preferably, third threshold A represents a value lower than the first threshold X in order to prevent charger 20 from oscillating between states in the flowchart. Accordingly, third threshold A may be about 16.8 volts for a vehicle battery rated for 12 volts. If the input voltage V_(IN) is larger than third threshold A, then the charger 20 returns to ST7 and/or ST8 until the input voltage V_(IN) is equal to or smaller than third threshold A, or battery pack 10 is removed.

If input voltage V_(IN) is not greater than a third threshold A, then controller 21 and/or microprocessor 23 then preferably checks whether input voltage V_(IN) is smaller than a fourth threshold B (ST10). Preferably, fourth threshold B is a value higher than second threshold Y in order to prevent charger 20 from oscillating between states in the flowchart. Accordingly, fourth threshold B may be about 10.7 volts for a vehicle battery rated for 12 volts. If the input voltage V_(IN) is smaller than fourth threshold B, then the charger 20 returns to ST7 and/or ST8 until the input voltage V_(IN) is equal to or smaller than third threshold A, or battery pack 10 is removed.

If (a) input voltage V_(IN) is not greater than a third threshold A and (b) input voltage V_(IN) is not smaller than a fourth threshold B, it is preferable to turn on current source 22 (and thus the output current I_(OUT)) (ST11) for a limited amount of time, such as 10 milliseconds. The controller 21 and/or microprocessor 23 may again read input voltage V_(IN) (ST12) to in effect check the battery pack's reaction to output current I_(OUT). After such reading, it is preferable to turn off current source 22 (and thus the output current I_(OUT) (ST13). Turning on and off current source 22 allows the controller 21 to check the battery pack's reaction without sending too much current, which may damage the battery pack 10.

The controller 21 and/or microprocessor 23 then preferably checks whether input voltage V_(IN) is greater than a fifth threshold C (ST14). Preferably, fifth threshold C represents a value higher than fourth threshold B. Accordingly, fifth threshold C may be about 10.2 volts for a vehicle battery rated for 12 volts. If the input voltage V_(IN) is larger than fifth threshold C, then the charger 20 returns to ST3, so that charging of battery pack 10 can continue. Persons skilled in the art shall recognize that, if an error signal was displayed, such signal can be ended or removed.

However, if input voltage V_(IN) is not greater than a fifth threshold C, the counter can be decreased (ST15). If the counter is zero (ST16), then the charger 20 returns to ST7 and/or ST8 until the input voltage V_(IN) is equal to or smaller than third threshold A, or battery pack 10 is removed.

If the counter is not zero, controller 21 and/or microprocessor 23 then preferably checks whether a phase back flag has been set (ST17). If such flag has been set, then the charger 20 returns to ST7 and/or ST8 until the input voltage V_(IN) is equal to or smaller than third threshold A, or battery pack 10 is removed.

If the phaseback flag has not been set, then controller 21 and/or microprocessor 23 then preferably control current source 22 to lower, or phase back, the output current I_(OUT) (ST18). Preferably, the output current I_(OUT) is lowered from about 2 amps to about 1.3 amps for the rest of the charging process.

Because of the lowered output current I_(OUT), it may be preferable to clear the memory stacks which contain input voltage V_(IN) and/or battery pack temperature information (ST18, ST19, respectively), so as to not trigger a termination algorithm prematurely.

In addition, it is preferable to set the phaseback flag (ST21). After setting the flag, the charger 20 can then return to ST7 and/or ST8 until the input voltage V_(IN) is equal to or smaller than third threshold A, or battery pack 10 is removed.

It may also be preferable for the microprocessor 23 to lower the output current I_(ON) (e.g., from 2.0 amps to 1.3 amps) if the battery pack voltage V_(PACK) is above a certain threshold, such as about 34 volts. Like before, this is preferably done to avoid the opening of fuse 2.

Charger 20 may also have protective circuits other than foldback circuit 26. For example, it is preferably to provide a circuit to turn off current source 22 if the output current ION is on and the battery pack 10 is removed. This could create a large voltage spike across the B+ and B− terminals, which could damage components within charger 20.

Rather than relying on the analog/digital inputs of microprocessor 23, it is preferably to use a high speed input in microprocessor 23, so that if the desired signal is received, the microprocessor 23 would turn current source 22 off. Persons skilled in the art will recognize that such high speed input is pin P24 of microprocessor 23. In addition, persons skilled in the art will recognize how the type of signal received by microprocessor 23 via pin P24 from examining FIG. 2B.

It is also preferable to provide a watchdog circuit 27 that monitors whether microprocessor 23 is in control of current source 22. In a preferred embodiment, watchdog circuit 27 monitors pulses given at a specific interval by the microprocessor 23. In the event that the microprocessor 23 fails to provide such pulses at the predetermined interval, the watchdog circuit 27 preferably bypasses the microprocessor 23 and preferably disables current source 22 and/or DC mains power supply 24. The disabled current source 22 and/or DC mains power supply 24 will preferably remain disabled until power is removed from charger 20.

The watchdog circuit 27 preferably has two resettable timers. These two timers are used to provide a margin of error before the watchdog circuit 27 disables current source 22 and/or DC mains power supply 24, to prevent nuisance or undesired tripping of the watchdog circuit 27. Typically, this margin of error is a factor of five. In other words, microprocessor 23 would have to miss five pulses before the watchdog circuit 27 disables current source 22 and/or DC mains power supply 24.

Referring to FIG. 2B, transistors Q1, Q2 are ultimately controlled by microprocessor 23 to provide pulses. When these pulses are present, a voltage is developed across capacitor C20, which in turn allows C31 to charge. Preferably, the microprocessor shuts down the current source 22 for about 33 milliseconds in every one-second period.

This allows capacitor C20 to discharge through resistor R38. Since amplifier U3:B is preferably in a voltage follower configuration, capacitor C31 preferably discharges into pin 7 of amplifier U3:B.

If the microprocessor does not shut down current source 22 at the specified interval, capacitor C3 1 will continue to charge until the voltage reaches approximately the zener voltage V_(Z) of diode D35. This allows current to flow through the base of transistor Q7, which starts to turn on transistor Q7. This in turn starts transistor Q8 conducting, which in turn supplies more current through diode 41 to the base of transistor Q7, making transistor Q7 to conduct more current. This feedback process continues until the circuit is latched with transistors Q7, Q8 substantially, if not fully, saturated.

When the voltage at the collector of transistor Q8 is equal to or greater than the sum of zener voltage V_(Z) of diode D40, forward bias voltage V_(F) of diode D8 and one volt (i.e., the shutdown voltage of integrated circuit U2), integrated circuit U2 is forced into an overcurrent condition and shuts down current source 22. The watchdog circuit 27 will thus remain latched in this state until the power is removed from charger 20.

Persons skilled in the art will recognize that the watchdog circuit 27 may have three sections: a first timer, a second timer and a latch. The first timer will include capacitor C19, which preferably couples drain pulese to form a voltage across resistor R38, capacitor C20 and diode D12. The timer is formed by the voltage decay of resistor R38 and capacitor C20 when the drain pulses are not present. Diode D13 preferably discharges capacitor C19. Resistor R37 limits the current into diode D12. Diode 23 blocks any discharge of capacitor C20 except through resistor R38. Diode D 12 sets a maximum voltage on this timer circuit. Resistor R21 limits current into pin 5 of amplifier U3:B.

The second timer includes capacitor C31, resistor R66, which charges capacitor C31, diode D10, which prevents pin 7 of amplifier U3:B from charging capacitor C31, and amplifier U3:B, which discharges capacitor C31.

The latch includes resistor R39, which allows the voltage to rise at the base of transistor Q7 regardless of the potential across capacitor C31, diode D35, which sets the latch trip voltage, and capacitor C32, which filters noise across diode D35. As discussed above, the latch includes transistors Q7, Q8, which create a feedback loop, as well as resistor R70, which limits current through the base of transistor Q8, resistor R63, which sets the gain of transistor Q8, and resistor R71, which limits the current going into the base of transistor Q7. Furthermore, the latch includes resistor R65, which insures that diode D35 is at VZ**, diode D41, which prevents voltage across capacitor C31 from influencing pin 3 of integrated circuit U2, diode D40, which insures a latched state before shut down, diode D32, which prevents voltage a pin 3 of integrated circuit U2 from being exceeded, and resistor R64, which limits current through diode D32. Finally, the latch includes a diode D8, which prevents the watchdog circuit to influence the charger circuitry during normal charger operation.

Referring to FIG. 2B, the values of the different components of an exemplary charger according to the invention are as follows: C1 1200 microfarads/35 V C2 1200 microfarads/35 V C3 1200 microfarads/35 V C4 0.1 microfarads/50 V C5 0.068 microfarads/100 V C6 0.1 microfarads C7 10 microfarads/25 V C8 470 picofarads/500 V C9 470 picofarads/500 V C10 47 microfarads/250 V C11 0.1 microfarads C12 2700 picofarads/50 V C13 0.1 microfarads C14 0.01 microfarads C15 1800 picofarads C16 0.1 microfarads C17 5.6 nanofarads C18 0.1 microfarads C19 2200 picofarads/500 V C20 0.22 microfarads C22 1 microfarads/25 V C23 0.1 microfarads C24 0.001 microfarads C25 0.1 microfarads C26 0.1 microfarads C27 0.1 microfarads/25 V C28 0.01 microfarads C29 0.1 microfarads C30A 1 microfarads/100 V C31 47 microfarads/50 V C32 0.1 microfarads C33 0.1 microfarads C36 1200 microfarads/35 V D2 20 v Zener D3 IN4973 D4 MUR460 D5 MUR460 D6 1OMQ060N D7 10MQ060N D8 IN4148 D10 IN4148 D12 IN5242 D13 IN4148 D16 33 V Zener D17 IN4148 D18 LED D19 IN4148 D20 IN4148 D21 IN4148 D22 IN4148 D23 IN4148 D24 IN4937 D25 IN5231B D26 11DQ06 D27 IN4148 D28 6.8 V Zener D29 IN4148 D32 IN5231B D35 IN5231B D36 10MQ060N D39 P6KE91A D40 6.2 V Zener D41 1N4148 D42 36 V Zener D43 51 V Zener L1 Rod Core L2 Rod Core L3: B Choke L4 550 microhenries Q1 IRF3205 Q2 IRF3205 Q3 2N3904 Q4 BSH105 Q5 2N3904 Q6 BSH105 Q7 MMBT3904 Q8 MMBT3906 Q9 ZTX449 Q10 ZTX549 R1 43 kiloohms R2 1 kiloohms R3 510 ohms R5 100 ohms R7 18 ohms R8 18 ohms R9 2.05 kiloohms R10 150 ohms R13 13.7 ohms R14 392 ohms R15 1 kiloohms R16 1.82 kiloohms R17 1.82 kiloohms R18 1 kiloohms R19 10 kiloohms R20 22.1 kiloohms R21 10 kiloohms R24 1 kiloohms R25 10 kiloohms R26 10 kiloohms R27 80.6 kiloohms R28 9.09 kiloohms R29 2 kiloohms R30 2 kiloohms R31 27.4 kiloohms R32 15.0 kiloohms R33 39 kiloohms R34 51 kiloohms R35 10 kiloohms R36 1 kiloohms R37 300 ohms R38 10 kiloohms R39 10 kiloohms R41 90.9 kiloohms R42 30.9 kiloohms R43 390 ohms R44 100 ohms R45 8.25 kiloohms R46 1 kiloohms R47 10 kiloohms R48 100 ohms R49 1 kiloohms R50 0.12 ohms R51 1.82 kiloohms R53 665 ohms R54 10 kiloohms R56 1 kiloohms R57 2 kiloohms R58 332 ohms R59 90.9 kiloohms R60 120 ohms R63 1.5 kiloohms R64 330 ohms R65 30 kiloohms R66 200 kiloohms R68 200 kiloohms R70 1.2 kiloohms R71 1.2 kiloohms R72 200 kiloohms R73 200 kiloohms R74 11.8 ohms R75 11.8 ohms R76 124 kiloohms R77 11.5 ohms Microprocessor 23 Zilog Z86C83 U2 UC3845 U3 LM358 U4 5 volt, 2% VR1 10 kiloohms potentiometer X1 3.58 megahertz Z1 15G330K

Referring to FIG. 4, an alternate charger and battery pack combination is shown, wherein like numerals designate like parts. One major difference between the prior charger and the present charger is that the present charger 20, and its elements within, including controller 21, microprocessor 23, and current source 22, receive the necessary power from an AC mains power supply 24′, rather than DC mains power supply 24.

It is preferable to provide a watchdog circuit 27 that monitors whether controller 21 and/or microprocessor 23 are in control of current source 22, and/or that the current source 22 is responding to commands from controller 21 and/or microprocessor 23. In a preferred embodiment, watchdog circuit 27 monitors pulses given at a specific interval by the microprocessor 23. In the event that the microprocessor 23 fails to provide such pulses at the predetermined interval, the watchdog circuit 27 preferably bypasses the microprocessor 23 and preferably disables current source 22 and/or AC mains power supply 24′. The disabled current source 22 and/or AC mains power supply 24′ will preferably remain disabled until power is removed from charger 20.

One embodiment of watchdog 27 is shown in FIGS. 5-6. Terminal C is preferably connected to the output of current source 22 and the battery pack 10. In addition, terminal C may receive an oscillating voltage, which is preferably rectified and filtered by diode D38′ and capacitor C27′. The microprocessor 23 basically superimposes a signal on the current source output by disabling the current source 22 for a predetermined period of time, e.g., 10 milliseconds once every second. The 10 ms signal allows capacitor C27′ to discharge, limiting the current through transistor Q12′.

When transistor Q12′ does not conduct, current preferably flows through resistors R84′, R86′, causing transistor Q13′ to conduct. When transistor Q13′ conducts, capacitor C29′ is preferably discharged. The periodicity of the 10 ms signal prevents the voltage across capacitor C29′ from rising to a level sufficient to trigger the latching circuit formed by transistors Q14′, Q15′.

If the 10 ms signal pulse did not happen once during a period of about 2-3 seconds, the supply voltage from terminal A charges capacitor C29′ through resistor R85′ beyond the threshold, actuating latching circuit Q14′, Q15′. When the latching circuit latches, the voltage between terminals A, B goes down to 1 volt, disabling the current source 22.

Referring to FIGS. 5-6, the values of the different components of an exemplary charger according to the invention are as follows: C1′ 0.22 microfarads, 10%, 400 VDC C3′ 100 microfarads, 250 V C5′ 100 microfarads, 10 V, 20%, C6′ 1000 picofarads, 1 KV, 20% C7′ 1 microfarad, 35 V, 20% C8′ 1000 picofarads, 1 KV, 20% C9′ 0.1 microfarad, 50 V, 10% C12′ 1 microfarad, 35 V, 20% C13′ 100 picofarads, 50 V, 10% C14′ 1000 picofarads, 50 V, 10% C15′ 22 microfarads, 35 V, 20% C16′ 1 microfarad, 35 V, 20% C17′ 10 microfarads, 100 V C27′ 0.1 microfarad, 50 V, 10% C28′ 0.01 microfarads, 50 V, 10% C29′ 100 microfarads, 50 V, 20% C30′ 0.1 microfarad, 50 V, 10% D1′ 1N4006 D2′ 1N4006 D3′ 1N4006 D4′ 1N4006 D5′ 1N4006 D6′ 1N4006 D8′ (LED) RED D9′ 5.1 V, 5%, ½ W, SMT D10′ 18 V, 5PCT, ½ W, SMT D12′ 1N5248B D14′ 1N4937 D15′ 1N4148 D16′ 4 A, 600 V, UFR (MUR460) D17′ 1N4148 D19′ 1N5267B D21′ 75 V, SMT (1N4148W) D22′ 1N4006 D23′ 51 V, .5 W, LEADED (P6KE51A) D24′ 1N5257B D29′ 75 V, SMT (1N4148W) D34′ 1N4937 D38′ 1N4937 F1′ 2 amps, 250 V L1′ 100 microhenries L2′ 4.3 millihenries LFU1005V03 Q1′ IRF644 Q2′ 2N3906 Q3′ 2N3904 Q4′ 2N3906 Q5′ 2N3904 Q6′ 2N5551 Q7′ 2N3904 Q12′ 2N3904 Q13′ 2N3904 Q14′ 2N3906 Q15′ 2N3904 R1′ 150 kiloohms R2′ 7.5 kiloohms R3′ 7.5 kiloohms R5′ 1 kiloohms R6′ 39 kiloohms R7′ 10 ohms R8′ 200 ohms R9′ 2.2 kiloohms R11′ 510 ohms R12′ 100 ohms R13′ 100 ohms R14′ 2.7 kiloohms R15′ 47 kiloohms R16′ 36 kiloohms R17′ 47 kiloohms R18′ 300 kiloohms R19′ 4.02 kiloohms R20′ 620 kiloohms R21′ 0.11 ohms R22′ 100 kiloohms R24′ 47.5 kiloohms R25′ 14 kiloohms R26′ 80.6 kiloohms R27′ 240 kiloohms R28′ 7.5 kiloohms R31′ 240 kiloohms R34′ 5.1 kiloohms R35′ 33 kiloohms R36′ 8.25 kiloohms R37′ 10 kiloohms R38′ 33 kiloohms R39′ 8.2 kiloohms R40′ 158 kiloohms R42′ 2.4 ohms R47′ 82 kiloohms R48′ 82 kiloohms R49′ 100 kiloohms (NTC thermistor) R51′ 1 kiloohms R52′ 33 kiloohms R53′ 360 kiloohms R54′ 120 kiloohms R55′ 240 kiloohms R65′ 100 kiloohms R68′ 10 kiloohms R70′ 100 kiloohms R71′ 270 kiloohms R81′ 24 kiloohms R82′ 10 kiloohms R83′ 10 kiloohms R84′ 10 kiloohms R85′ 51 kiloohms R86′ 5.1 kiloohms R87′ 47 ohms R88′ 470 kiloohms R89′ 47 kiloohms R90′ 510 ohms R91′ 240 ohms R92′ 100 ohms

U1′ PIC16C717 from Microchip Technologies

Persons skilled in the art will recognize that the sensing terminal, i.e., terminal C, of watchdog circuit 27 is hard-wired onto the output of current source 22. However, this need not be so. Referring to FIGS. 7-8, watchdog circuit 27′ is preferably inductively connected to the output of current source 22.

Preferably, a wire loop WL is used to detect, by means of magnetic induction, the presence of a periodic signal superimposed by controller 21 (or microprocessor 23) upon the output of current source 22. The detected superimposed periodic signal is demodulated by watchdog circuit 27′. Like before, the microprocessor 23 basically superimposes a signal on the current source output by disabling the current source 22 for 10 milliseconds once every second.

Watchdog circuit 27′ preferably has several loops of wire forming wire loop WL. The loops are placed around or in proximity to the main inductor (not shown) of current source 22. The flux linkage between wire loop WL and the main inductor imposes a voltage across wire loop WL. Voltage across wire loop WL in turn forces current to flow through diodes D38′, D39′. Current through diode D38′ in turn excites the filter network formed by resistors R92′, R93′ and capacitor C31′.

As current flows, capacitor C31′ is charged, promoting current flow through resistor R94′ and causing transistor Q16′ to conduct. In other words, detection of the 10 ms signal preferably excites the filter by charging capacitor C31′, promoting current flow through resistor R94′ and causing transistor Q16′ to conduct.

When transistor Q16′ conducts, current through resistor R95′ is preferably limited, thus preventing transistor Q17′ from conducting. When transistor Q17′ does not conduct, current through diode D39′ is allowed to charge capacitor C32′ with a time constant effectively programmed by resistor R96′. If the voltage across capacitor C32′ rises to a sufficient level, then the latching circuit formed by resistors R97′, R98′, and transistors Q18′, Q19′ is triggered. Such latching circuit can be used to short (and preferably disable) the current source 22.

When the current source 22 is disabled for 10 ms, no voltage is created through wire loop WL. Because no current then flows through diodes D38′, D39′, capacitor C31′ can discharge. The discharge of capacitor C1 in effect limits the current through resistor R94′ and transistor Q16′, preventing transistor Q16′ from conducting.

When transistor Q16′ does not conduct, current flows through resistors R99′, R95′, thus causing transistor Q17′ to conduct. When transistor Q17′ conducts, capacitor C32′ preferably discharges with a time constant effectively programmed by resistor R100′. However, the periodicity of the 10 ms signal prevents the voltage across capacitor C32′ from rising to a level sufficient to trigger the latching circuit formed by resistors R97′, R98′, and transistors Q18′, Q19′.

Persons skilled in the art will recognize that the watchdog circuits 27, 27′ are preferably not connected to the low reference voltage, i.e., ground, in chargers. This obviates the need for expensive high voltage parts, such as high voltage resistors and switches, to handle 120-150 volts.

Finally, persons skilled in the art may recognize other additions or alternatives to the means disclosed herein. However, all these additions and/or alterations are considered to be equivalents of the present invention. 

1. A charger for charging a battery pack, the charger comprising: a battery power source providing power to the battery pack, the battery power source having first and second power settings at which power is provided to the battery pack at a first and second power levels corresponding to the first and second power settings; a controller connected to and controlling the battery power source; and a power supply connectable to an outside power source, the power supply receiving a current and voltage from the outside power source for providing power to at least one of the controller and the battery power source; wherein the controller comprises a foldback circuit for switching between the first and second power settings depending upon at least one of the current and voltage received from the outside power source.
 2. The charger of claim 1, wherein the outside power source is a vehicle battery.
 3. The charger of claim 1, wherein the foldback circuit monitors voltage of the battery pack.
 4. The charger of claim 1, wherein the first and second power settings are high and low output current settings, respectively.
 5. The charger of claim 4, wherein the foldback circuit switches between the first and second power settings before the current from the outside power source reaches a certain threshold.
 6. The charger of claim 1, wherein the controller includes at least part of the foldback circuit. 7-16. (canceled) 